Track-and-hold charge pump and pll

ABSTRACT

Track-and-hold charge pumps and PLL are provided. A track-and-hold charge pump includes a track-and-hold circuit, a transconductance amplifier, a pulse width modulator (PWM), and a pumping switch coupled to the transconductance amplifier. The track-and-hold circuit samples an input signal according to a reference clock. The transconductance amplifier converts the sampled input signal into a current. The PWM provides a PWM signal according to the reference clock. The pumping switch is controlled by the PWM signal, to provide an output current according to the current.

BACKGROUND

Phase locked loops (PLL) are commonly used in circuits that generate ahigh-frequency signal with a frequency being a multiple of the frequencyof a reference signal. PLLs can also be found in applications where thephase of the output signal tracks the phase of the reference signal,hence the name phase-locked loop. For example, a PLL can be used in thefrequency synthesizer of a radio receiver or transmitter for generatinga local oscillator signal, which is a multiple of a stable, low-noiseand often temperature-compensated reference signal. In another example,a PLL can be used for clock recovery applications in digitalcommunication systems, disk-drive read-channels, etc.

BRIEF DESCRIPTION OF THE DRAWINGS

Aspects of the present disclosure are best understood from the followingdetailed description when read with the accompanying figures. It shouldbe noted that, in accordance with the standard practice in the industry,various features are not drawn to scale. In fact, the dimensions of thevarious features may be arbitrarily increased or reduced for clarity ofdiscussion.

FIG. 1 shows a phase-locked loop (PLL), in accordance with someembodiments of the disclosure.

FIG. 2A shows a track and hold charge pump, in accordance with someembodiments of the disclosure.

FIG. 2B shows a track and hold charge pump, in accordance with someembodiments of the disclosure.

FIG. 3 shows a PLL, in accordance with some embodiments of thedisclosure.

FIG. 4A shows a track and hold charge pump with an adjustable pulsewidth, in accordance with some embodiments of the disclosure.

FIG. 4B shows a track and hold charge pump with an adjustable pulsewidth, in accordance with some embodiments of the disclosure.

FIG. 5A shows a track and hold charge pump with an adjustabletransconductance (Gm), in accordance with some embodiments of thedisclosure.

FIG. 5B shows a track and hold charge pump with an adjustable Gm, inaccordance with some embodiments of the disclosure.

FIG. 6A shows a track and hold charge pump with an adjustable slew rate,in accordance with some embodiments of the disclosure.

FIG. 6B shows a track and hold charge pump with an adjustable slew rate,in accordance with some embodiments of the disclosure.

FIG. 7 shows a converter, in accordance with some embodiments of thedisclosure.

FIG. 8 shows a bandwidth tracking circuit, in accordance with someembodiments of the disclosure.

FIG. 9 shows a flow chart illustrating the operations of a PLL, inaccordance with some embodiments of the disclosure.

DETAILED DESCRIPTION

The following disclosure provides many different embodiments, orexamples, for implementing different features of the subject matterprovided. Specific examples of components and arrangements are describedbelow to simplify the present disclosure. These are, of course, merelyexamples and are not intended to be limiting. In some embodiments, theformation of a first feature over or on a second feature in thedescription that follows may include embodiments in which the first andsecond features are formed in direct contact, and may also includeembodiments in which additional features may be formed between the firstand second features, such that the first and second features may not bein direct contact. In addition, the present disclosure may repeatreference numerals and/or letters in the various examples. Thisrepetition is for the purpose of simplicity and clarity and does not initself dictate a relationship between the various embodiments and/orconfigurations discussed.

Some variations of the embodiments are described. Throughout the variousviews and illustrative embodiments, like reference numbers are used todesignate like elements. It should be understood that additionaloperations can be provided before, during, and/or after a disclosedmethod, and some of the operations described can be replaced oreliminated for other embodiments of the method.

FIG. 1 shows a phase-locked loop (PLL) 100, in accordance with someembodiments of the disclosure. The PLL 100 is an analog PLL capable ofmultiplying a low-frequency reference clock CK_(REF) to generate ahigh-frequency output clock CK_(PLL). The PLL 100 includes a track andhold (T/H) charge pump 110, a frequency tracking circuit 120, a low passfilter 130, a voltage-controlled oscillator (VCO) 140, and a frequencydivider 150.

The track and hold charge pump 110 is coupled between the frequencydivider 150 and a node N1. The track and hold charge pump 110 comparesthe phases of a feedback signal CK_(DIV) from the frequency divider 150and the reference clock CK_(REF), to generate a pumping current Ip, andthe pumping current Ip is proportional to the difference between thephases of the feedback signal CK_(DIV) and the reference clock CK_(REF).

The frequency tracking circuit 120 is also coupled between the frequencydivider 150 and the node N1. The frequency tracking circuit 120 iscapable of presetting the output clock CK_(PLL) at target frequency,e.g. decreasing the frequency error between the feedback signal CK_(DIV)and the reference clock CK_(REF). The frequency tracking circuit 120provides a frequency-locked loop (FLL) for the VCO 140. In someembodiments, the FLL has a larger gain than a core loop formed by thetrack and hold charge pump 110, the LPF 130, the VCO 140 and thefrequency divider 150. After locking frequency is achieved, thefrequency error between the feedback signal CK_(DIV) and the referenceclock CK_(REF) is small, and then the frequency tracking circuit 120 canbe disabled to save power.

The LPF 130 is coupled between the node N1 and the VCO 140. The LPF 130is capable of filtering a pumping signal S_(N1) corresponding to thepumping current Ip at the node N1, to generate a control voltageV_(CTRL) to the VCO 140.

The VCO 140 is coupled between the LPF 130 and the frequency divider150. The VCO 140 is capable of generating the output clock CK_(PLL)according to the control voltage V_(CTRL).

The frequency divider 150 is coupled to the VCO 140, and is capable ofdividing the output clock CK_(PLL) to obtain the feedback signalCK_(DIV), and providing the feedback signal CK_(DIV) to the track andhold charge pump 110 and the frequency tracking circuit 120.

In some embodiments, the frequency divider 150 is capable of providing apair of different feedback signals CK_(DIV+) and CK_(DIV−) to the trackand hold charge pump 110 and the frequency tracking circuit 120. Forexample, if the feedback signal CK_(DIV+) is identical to the feedbacksignal CK_(DIV), the feedback signal CK_(DIV−) is complementary to thefeedback signal CK_(DIV). Conversely, if the feedback signal CK_(DIV−)is identical to the feedback signal CK_(DIV), the feedback signalCK_(DIV+) is complementary to the feedback signal CK_(DIV).

FIG. 2A shows a track and hold charge pump 200A illustrating anexemplified block diagram of the track and hold charge pump 110 of FIG.1, in accordance with some embodiments of the disclosure. The track andhold charge pump 200A includes a pulse width modulator (PWM) 210, apumping switch 240, a transconductance amplifier (OTA) 220, a samplingswitch 250A, a capacitive element C1 (e.g. a capacitor), and a voltagedivider 230.

The sampling switch 250A is a sample-and-hold circuit coupled to thecapacitive element C1 and a non-inverting input terminal of the OTA 220,and the capacitive element C1 is coupled between the non-inverting inputterminal of the OTA 220 and a ground GND. The sampling switch 250A iscontrolled by the reference clock CK_(REF). When the sampling switch250A is turned on by the reference clock CK_(REF), the feedback signalCK_(DIV) is sampled and stored in the capacitive element C1 as a voltageV_(SP).

The OTA 220 has a non-inverting input terminal for receiving the voltageV_(SP) stored in the capacitive element C1 and an inverting inputterminal for receiving a reference voltage V_(CM). The OTA 220 iscapable of converting a voltage difference between the voltage V_(SP)and the reference voltage V_(CM) into a current I_(OTA). In suchembodiments, the OTA 220 is operated in the single-ended form (or mode).

In some embodiments, the reference voltage V_(CM) is provided by thevoltage divider 230. The voltage divider 230 includes a resistor R1coupled between a power supply VDD and the inverting input terminal ofthe OTA 220, and a resistor R2 coupled between a ground GND and theinverting input terminal of the OTA 220. In some embodiments, thereference voltage V_(CM) is provided by a reference circuit, such as aband gap circuit.

The PWM 210 receives the reference clock CK_(REF) and modifies the pulsewidth of the reference clock CK_(REF) to provide a control signalCK_(PWM) to the pumping switch 240.

The pumping switch 240 is controlled by the control signal CK_(PWM) fromthe PWM 210. When the pumping switch 240 is turned on by the controlsignal CK_(PWM), the track and hold charge pump 200A is operating in acharging state, and is capable of providing a pumping current Ip to theLPF 130 in FIG. 1 according to the current I_(OTA). As described above,The LPF 130 of FIG. 1 filters a pumping signal S_(N1) corresponding tothe pumping current Ip to provide the control voltage V_(CTRL), so as tocontrol the VCO 140 in the PLL 100 of FIG. 1. Conversely, when thepumping switch 240 is turned off by the control signal CK_(PWM), thetrack and hold charge pump 200A is operating in a discharging state, andno pumping current Ip is provided.

In some embodiments, a single pumping switch (i.e. the pumping switch240) is used in the track and hold charge pump 200A, thereby avoidingmismatch between an up switch (e.g. a charging switch for charging aloop filter) and a down switch that are commonly used in a general PLLin other approaches (e.g. a discharging switch for discharging the loopfilter). The mismatch between the up and down switches in otherapproaches leads to worse spur performance for a charge pump.

FIG. 2B shows a track and hold charge pump 200B illustrating anotherexemplified block diagram of the track and hold charge pump 110 of FIG.1, in accordance with some embodiments of the disclosure. The track andhold charge pump 200B includes a pulse width modulator 210, a pumpingswitch 240, an OTA 220, two sampling switches 250A and 250B, and twocapacitive elements C1 and C2.

The sampling switch 250A is coupled to the capacitive element C1 and anon-inverting input terminal of the OTA 220, and the capacitive elementC1 is coupled between the non-inverting input terminal of the OTA 220and a ground GND. The sampling switch 250B is coupled to the capacitiveelement C2 and an inverting input terminal of the OTA 220, and thecapacitive element C2 is coupled between the inverting input terminal ofthe OTA 220 and the ground GND. The sampling switches 250A and 250B arecontrolled by the reference clock CK_(REF) together. When the samplingswitch 250A is turned on by the reference clock CK_(REF), the feedbacksignal CK_(DIV+) is sampled and stored in the capacitive element C1 as avoltage V_(SP1). Simultaneously, the sampling switch 250B is also turnedon by the reference clock CK_(REF), and the feedback signal CK_(DIV−) issampled and stored in the capacitive element C2 as a voltage V_(SP2).

The OTA 220 is capable of converting a voltage difference between thevoltages V_(SP1) and V_(SP2) into a current I_(OTA). In suchembodiments, the OTA 220 is operated in the differential-ended form (ormode).

As described above, the PWM 210 receives the reference clock CK_(REF)and modifies the pulse width of the reference clock CK_(REF) to providea control signal CK_(PWM) to the pumping switch 240, so as to controlthe pumping switch 240. When the pumping switch 240 is turned on by thecontrol signal CK_(PWM), the track and hold charge pump 200B isoperating in a charging state, and is capable of providing a pumpingcurrent Ip to the LPF 130 of FIG. 1 according to the current I_(OTA).Furthermore, The LPF 130 filters the pumping signal S_(N1) correspondingto the pumping current Ip to provide the control voltage V_(CTRL), so asto control the VCO 140 in the PLL 100 of FIG. 1. Conversely, when thepumping switch 240 is turned off by the control signal CK_(PWM), thetrack and hold charge pump 200B is operating in a discharging state, andno pumping current Ip is provided.

In some embodiments, a single pumping switch (i.e. the pumping switch240) is used in the track and hold charge pump 200B, thereby avoidingmismatch between an up switch (e.g. a charging switch for charging aloop filter) and a down switch that are commonly used in a general PLLin other approaches (e.g. a discharging switch for discharging the loopfilter). The mismatch between the up and down switches in otherapproaches leads to worse spur performance for a charge pump.

For analog PLLs, the process, supply voltage, and temperature (PVT)variations give rise to not only uncertainty of the VCO gain but alsouncertainty of the current of charge pump. Therefore, bandwidthstabilization, tracking, or optimization techniques are highlydesirable.

The bandwidth (also called loop bandwidth, noise bandwidth orsingle-sided loop bandwidth) determines the frequency and phase locktime of a PLL. Since the PLL is a negative feedback system, phase marginand stability issues must be considered. Many of these parameters areinteractive for a PLL. For example, lower values of bandwidth lead toreduced levels of phase noise and reference spurs, but at the expense oflonger lock times and less phase margin.

When the bandwidth is widened, an output signal of the PLL can betracked more quickly, but the jitters on the output signal areincreased. A narrow bandwidth will have more trouble tracking the outputsignal, but will result in a cleaner signal and will give a moreaccurate representation of the output signal.

If the bandwidth is very narrow, the PLL will have trouble acquiring andmaintaining an accurate phase lock. A very narrow bandwidth will rejectmost noise and will give a very clean output signal. However, it is hardto maintain a phase lock on a noisy signal as the time between locklosses can be proportional to the SNR of the output signal. Furthermore,a wider bandwidth is needed for PLL applications where the signalbecomes noisy or where it is not so vital for the clock to be absolutelyaccurate. A bandwidth calibration circuit is used in a PLL toautomatically adjust bandwidth of the PLL. Operations of the PLLs havingthe bandwidth calibration circuit will be described below.

FIG. 3 shows a PLL 300 capable of automatically adjusting bandwidth, inaccordance with some embodiments of the disclosure. The PLL 300 is ananalog PLL capable of multiplying a low-frequency reference clockCK_(REF) to generate a high-frequency output clock CK_(PLL). The PLL 300includes a track and hold charge pump 310, a frequency tracking circuit120, a low pass filter 130, a VCO 140, a frequency divider 150, and abandwidth calibration circuit 320.

Compared with the PLL 100 of FIG. 1, the PLL 300 further includes thebandwidth calibration circuit 320 coupled to the LPF 130 via the nodeN1. The bandwidth calibration circuit 320 is capable of providing abandwidth control signal BW_CTRL to control a charge pump gain of thetrack and hold charge pump 310. In some embodiments, the charge pumpgain is equivalent to the current magnitude of the pumping current Ipprovided by the track and hold charge pump 310, and the pumping currentIp can be formulated according to the following formula (1):

$\begin{matrix}{{I_{P} = {{Gm} \times \frac{W}{t_{r}} \times V_{DD}}},} & (1)\end{matrix}$

where Gm represents the gain (e.g. transconductance) of the OTA withinthe track and hold charge pump 310, W represents the pulse width of acontrol signal CK_(PWM) from a PWM within the track and hold charge pump310, V_(DD) represents a supply voltage of the track and hold chargepump 310, and t_(r) represents the rise time of the feedback signalCK_(DIV). The control signal CK_(PWM) will be described below.

In some embodiments, the bandwidth calibration circuit 320 includes aconverter 322 and a bandwidth tracking circuit 324. In response to thepumping signal S_(N1) at the node N1 corresponding to the pumpingcurrent Ip, the converter 322 provides a logic signal SIGN to indicatewhether the track and hold charge pump 310 is in a charging state or adischarging state. The bandwidth tracking circuit 324 provides thebandwidth control signal BW_CTRL according to the logic signal SIGN, soas to control the bandwidth of the PLL 300 by changing the charge pumpgain of the track and hold charge pump 310.

For the PLL 300, the bandwidth is associated with the pumping currentIp. Therefore, in order to change the bandwidth of the PLL 300, thebandwidth calibration circuit 320 is capable of providing the bandwidthcontrol signal BW_CTRL to change the gain of the OTA (e.g. Gm), thepulse width of the control signal CK_(PWM) (e.g. W), or a slew rate ofthe feedback signal CK_(DIV) corresponding to the rise time (e.g.t_(r)), so as to change the pumping current Ip.

FIG. 4A shows a track and hold charge pump 400A with an adjustable pulsewidth illustrating an exemplified block diagram of the track and holdcharge pump 310 of FIG. 3, in accordance with some embodiments of thedisclosure. The track and hold charge pump 400A includes a pulse widthmodulator 410, a pumping switch 240, an OTA 220, a sampling switch 250A,a capacitive element C1, and a voltage divider 230.

Compared with the track and hold charge pump 200A of FIG. 2A, the PWM410 receives the reference clock CK_(REF), and modifies the pulse widthof the reference clock CK_(REF) according to the bandwidth controlsignal BW_CTRL in the track and hold charge pump 400A, so as to providea control signal CK_(PWM) to the pumping switch 240. Specifically, thepulse width of the control signal CK_(PWM) is adjustable according tothe bandwidth control signal BW_CTRL.

Referring to FIG. 3 and FIG. 4A together, when the pumping switch 240 isturned on by the control signal CK_(PWM), the track and hold charge pump400A is operating in a charging state, and is capable of providing apumping current Ip to the LPF 130 of FIG. 3 according to the currentI_(OTA). Furthermore, the LPF 130 filters the pumping signal S_(N1)corresponding to the pumping current Ip to provide the control voltageV_(CTRL), so as to control the VCO 140 in the PLL 300 of FIG. 3.Conversely, when the pumping switch 240 is turned off by the controlsignal CK_(PWM), the track and hold charge pump 400A is operating in adischarging state, and no pumping current Ip is provided.

According to the previous formula (1), when the pulse width (e.g. W) ofthe control signal CK_(PWM) is increased by the bandwidth control signalBW_CTRL, the pumping current Ip is increased, and then the bandwidth ofthe PLL 300 of FIG. 3 is increased. Conversely, when the pulse width ofthe control signal CK_(PWM) is decreased by the bandwidth control signalBW_CTRL, the pumping current Ip is decreased, and then the bandwidth ofthe PLL 300 of FIG. 3 is decreased.

FIG. 4B shows a track and hold charge pump 400B with an adjustable pulsewidth illustrating another exemplified block diagram of the track andhold charge pump 310 of FIG. 3, in accordance with some embodiments ofthe disclosure. The track and hold charge pump 400B includes a pulsewidth modulator 410, a pumping switch 240, an OTA 220, two samplingswitches 250A and 250B, and two capacitive elements C1 and C2.

In the track and hold charge pump 400B, the OTA 220 is operated in thedifferential-ended form. Compared with the track and hold charge pump200B of FIG. 2B, the PWM 410 receives the reference clock CK_(REF), andmodifies the pulse width of the reference clock CK_(REF) furtheraccording to the bandwidth control signal BW_CTRL in the track and holdcharge pump 400B, so as to provide a control signal CK_(PWM) to thepumping switch 240. Specifically, the pulse width of the control signalCK_(PWM) is adjustable according to the bandwidth control signalBW_CTRL.

By using the bandwidth control signal BW_CTRL to modify the pulse widthof the control signal CK_(PWM) (i.e. the on and off states of thepumping switch 240), the pumping current Ip can be changed so as tochange the bandwidth of the PLL 300 of FIG. 3.

FIG. 5A shows a track and hold charge pump 500A with an adjustabletransconductance (Gm) illustrating another exemplified block diagram ofthe track and hold charge pump 310 of FIG. 3, in accordance with someembodiments of the disclosure. The track and hold charge pump 500Aincludes a pulse width modulator 210, a pumping switch 240, an OTA 420,a sampling switch 250A, a capacitive element C1, and a voltage divider230.

Compared with the track and hold charge pump 200A of FIG. 2A, the OTA420 is an amplifier with an adjustable Gm. The OTA 420 converts avoltage difference between the voltage V_(SP) and the reference voltageV_(CM) into a current I_(OTA) according to the bandwidth control signalBW_CTRL. In such embodiments, the OTA 420 is operated in thesingle-ended form.

According to the previous formula (1), when the gain of the OTA 420 isincreased by the bandwidth control signal BW_CTRL, the current I_(OTA)is increased, and then the pumping current Ip is increased. Furthermore,the bandwidth of the PLL 300 of FIG. 3 is increased when the pumpingcurrent Ip is increased. Conversely, when the gain of the OTA 420 isdecreased by the bandwidth control signal BW_CTRL, the pumping currentIp is decreased due to the current I_(OTA) being decreased, and then thebandwidth of the PLL 300 of FIG. 3 is decreased.

FIG. 5B shows a track and hold charge pump 500B with an adjustable Gmillustrating another exemplified block diagram of the track and holdcharge pump 310 of FIG. 3, in accordance with some embodiments of thedisclosure. The track and hold charge pump 500B includes a pulse widthmodulator 210, a pumping switch 240, an OTA 420, two sampling switches250A and 250B, and two capacitive elements C1 and C2.

In the track and hold charge pump 500B, the OTA 420 is operated in thedifferential-ended form. Compared with the OTA 220 of FIG. 2B, the OTA420 is capable of converting a voltage difference between the voltageV_(SP1) stored in the capacitive element C1 and the voltage V_(SP2)stored in the capacitive element C2 into a current I_(OTA) according tothe bandwidth control signal BW_CTRL. Therefore, by using the bandwidthcontrol signal BW_CTRL to control the gain of the OTA 420, the currentI_(OTA) is changed in response to the controlled gain of the OTA 420. Asdescribed above, the bandwidth of the PLL 300 is associated with thepumping current Ip, and the pumping current Ip can be changed inresponse to the changed current I_(OTA) so as to change the bandwidth ofthe PLL 300 of FIG. 3.

FIG. 6A shows a track and hold charge pump 600A with an adjustable slewrate illustrating another exemplified block diagram of the track andhold charge pump 310 of FIG. 3, in accordance with some embodiments ofthe disclosure. The track and hold charge pump 600A includes a pulsewidth modulator 210, a pumping switch 240, an OTA 220, a sampling switch250A, a capacitive element C1, a voltage divider 230, and a buffer (BUF)430A.

Compared with the track and hold charge pump 200A of FIG. 2A, the trackand hold charge pump 600A further includes the buffer 430A coupled tothe sampling switch 250A. The buffer 430A receives the feedback signalCK_(DIV) and changes the rise time t_(r) of the feedback signal CK_(DIV)to provide a signal CK_(tr) according to the bandwidth control signalBW_CTRL. Therefore, slew rate (defined as the change of voltage per unitof time) of the feedback signal CK_(DIV) is changed by the buffer 430A.In some embodiments, the buffer 430A is a driver with an adjustabledrive capability capable of changing the rise time t_(r) of the feedbacksignal CK_(DIV) and the drive capability is determined according to thebandwidth control signal BW_CTRL. Various circuits implemented as thebuffer 430A are within the contemplated scope of the present disclosure.

As described above, when the sampling switch 250A is turned on by thereference clock CK_(REF), the signal CK_(tr) is sampled and stored inthe capacitive element C1 as a voltage V_(SP). The OTA 220 converts avoltage difference between the voltage V_(SP) and the reference voltageV_(CM) into a current I_(OTA). In such embodiments, the OTA 220 isoperated in the single-ended form.

The PWM 210 receives the reference clock CK_(REF), and modifies thepulse width of the reference clock CK_(REF), so as to provide a controlsignal CK_(PWM) to the pumping switch 240.

According to the previous formula (1), when the slew rate (i.e. t_(r))of the feedback signal CK_(DIV) is decreased via the buffer 430Acontrolled by the bandwidth control signal BW_CTRL, the pumping currentIp is increased. Moreover, the bandwidth of the PLL 300 is increasedwhen the pumping current Ip is increased. Conversely, when the slew rateof the feedback signal CK_(DIV) is increased by the bandwidth controlsignal BW_CTRL, the pumping current Ip is decreased, and then thebandwidth of the PLL 300 of FIG. 3 is decreased.

FIG. 6B shows a track and hold charge pump 600B with an adjustable slewrate illustrating another exemplified block diagram of the track andhold charge pump 310 of FIG. 3, in accordance with some embodiments ofthe disclosure. The track and hold charge pump 600B includes a pulsewidth modulator 210, a pumping switch 240, an OTA 220, two samplingswitches 250A and 250B, two capacitive elements C1 and C2, and twobuffers 430A and 430B.

Compared with the track and hold charge pump 200B of FIG. 2B, the trackand hold charge pump 600B further includes the buffers 430A and 430Bcoupled to the sampling switches 250A and 250B, respectively. The buffer430A receives the feedback signal CK_(DIV+), and changes the rise timet_(r) of the feedback signal CK_(DIV+) to provide a signal CK_(tr+)according to the bandwidth control signal BW_CTRL. Simultaneously, thebuffer 430B receives the feedback signal CK_(DIV−), and changes the risetime t_(r) of the feedback signal CK_(DIV−) to provide a signal CK_(tr−)according to the bandwidth control signal BW_CTRL. Therefore, the slewrates of the feedback signals CK_(DIV+) and CK_(DIV−) are changed.

The buffers 430A and 430B have the same circuit and structure. In someembodiments, the buffers 430A and 430B are the drivers with anadjustable drive capability capable of changing the rise time t_(r) ofthe feedback signals CK_(DIV+) and CK_(DIV−), and the drive capabilityis determined according to the bandwidth control signal BW_CTRL.

By using the bandwidth control signal BW_CTRL to control the slew rateof the feedback signals CK_(DIV+) and CK_(DIV−), the pumping current Ipcan be changed so as to change the bandwidth of the PLL 300 of FIG. 3.

FIG. 7 shows a converter 700 illustrating an exemplified block diagramof the converter 322 of FIG. 3, in accordance with some embodiments ofthe disclosure. The converter 700 is a single-ended amplifier thatincludes a capacitive element C3, a string of self-biased inverters710_1-710_n, and a string of inverters 720_1-720_n.

The capacitive element C3 is an alternating current (AC) couplingcapacitive element coupled between the self-biased inverter 710_1 andthe node N1 of the PLL 300 of FIG. 3, and the self-biased inverter 710_1is an input self-biased inverter of the string of self-biased inverters710_1-710_n. Furthermore, the AC component of the pumping signal S_(N1)corresponding to the pumping current Ip at the node N1 of the PLL 300 ofFIG. 3 is coupled and input to the self-biased inverter 710_1 via thecapacitive element C3.

The self-biased inverters 710_1-710_n are coupled in series. Each of theself-biased inverters 710_1-710_n includes a PMOS transistor P1, an NMOStransistor N1, and a feedback resistor RF. The PMOS transistor P1 andthe NMOS transistor N1 form an inverter, and the feedback resistor RF iscoupled between the input and output terminals of the inverter. In someembodiments, the self-biased inverter is used as a small-signalamplifier for amplifying the AC component of the pumping signal S_(N1).

The inverters 720_1-720_m are coupled in series, and the inverter 720_1is coupled to the self-biased inverter 710_n. Each of the inverters720_1-720_m includes a PMOS transistor P2 and an NMOS transistor N2.

It should be noted that the number of biased inverters 710_1-710_n andthe number of inverters 720_1-720_m can be adjusted as long as the gainis enough to convert the AC component of the pumping signal S_(N1) intothe logic signal SIGN.

In some embodiments, the logic signal SIGN can be represented by “+1” or“−1”. For example, the logic signal SIGN with “+1” indicates that thetrack and hold charge pump is in a charging state, and the logic signalSIGN with “−1” indicates that the track and hold charge pump is in adischarging state.

FIG. 8 shows a bandwidth tracking circuit 800 illustrating anexemplified block diagram of the bandwidth tracking circuit 324 of FIG.3, in accordance with some embodiments of the disclosure. The bandwidthtracking circuit 800 includes a delay unit 810, multiple D flip-flops(DFFs) 820_1-820_k, multiple multipliers 830_1-830_k, an adder 840, anintegrator 850 and a multiplier 860.

The delay unit 810 is used to delay the logic signal SIGN into the DFFs820_1-820_k. For example, after an output clock CK_(PLL) of a PLL hasbeen locked, the delay unit 810 provides the delayed logic signalSIGN_(D) to the DFFs 820_1-820_k. In some embodiments, the desiredlatency of the delay unit 810 is implemented by inserting some DFFs.

The DFFs 820_1-820_k are coupled in series to shift the delayed logicsignal SIGN_(D) in response to a specific clock (e.g. the output clockCK_(PLL) or the reference clock CK_(REF)). In some embodiments, thenumber of DFFs 820_1-820_k is determined according to a minimal variable(e.g. resolution) of the bandwidth of the PLL.

The number of DFFs 820_1-820_k is identical to the number of multipliers830_1-830_k. Each of the multipliers 830_1-830_k is capable ofmultiplying the logic signal SIGN by the delayed logic signal from thecorresponding DFF to obtain a multiplication output. For example, themultiplier 830_1 multiplies the logic signal SIGN by the delayed logicsignal SIGN_(D-1) from the DFF 820_1 to obtain a multiplication outputMult_1, the multiplier 830_2 multiplies the logic signal SIGN by thedelayed logic signal SIGN_(D-2) from the DFF 820_2 to obtain amultiplication output Mult_2, and so on.

The adder 840 sums the multiplication outputs Mult_1-Mult_k to obtainthe sum Mult_SUM. The sum Mult_SUM is integrated by the integrator 850.The multiplier 860 multiplies the integrated sum Mult_SUM by a weightvalue W to obtain the bandwidth control signal BW_CTRL, and the weightvalue W is determined according to actual application.

In some embodiments, the bandwidth control signal BW_CTRL can beformulated according to the following formula (2):

BW_CTRL_(h)=BW_CTRL_(h-1)+w×(SIGN_(n)×SIGN_(n-D-1)+SIGN_(n)×SIGN_(n-D-2)+ . . .+SIGN_(n)×SIGN_(n-D-k))   (2),

where n denotes the iteration cycle and D denotes the delayed timeprovided by the delay unit 810.

FIG. 9 shows a flow chart illustrating the operations of a PLL (e.g. 100of FIG. 1 and 300 of FIG. 3), in accordance with some embodiments of thedisclosure. The PLL includes a track and hold charge pump 110/310, a lowpass filter 130, a VCO 140, and a frequency divider 150.

In operation S910, a feedback signal CK_(DIV) from the frequency divider150 is sampled according to a reference clock CK_(REF) in the track andhold charge pump 110/310. In some embodiments, the frequency divider 150is capable of providing a pair of different feedback signals CK_(DIV+)and CK_(DIV−), and the pair of different feedback signals issimultaneously sampled according to the reference clock CK_(REF) in thetrack and hold charge pump 110/310.

In operation S920, the sampled feedback signal CK_(DIV) is convertedinto a current I_(OTA) by an OTA 220/420 in the track and hold chargepump 110/310. In some embodiments, a voltage difference between thesampled feedback signal CK_(DIV) and a reference voltage V_(CM) isconverted into the current I_(OTA). In some embodiments, a voltagedifference between the sampled feedback signals CK_(DIV+) and CK_(DIV−)is converted into the current I_(OTA).

In operation S930, the pulse width of the reference clock CK_(REF) ismodified to provide the control signal CK_(PWM), and a single pumpingswitch 240 is controlled by the control signal CK_(PWM) to provide apumping current Ip according to the current I_(OTA). As described above,the pumping current Ip is proportional to the difference between thephases of the feedback signal CK_(DIV) and the reference clock CK_(REF).

In operation S940, a pumping signal S_(N1) corresponding to the pumpingcurrent Ip is filtered by the filter 130, thereby generating a controlvoltage V_(CTRL).

In operation S950, the VCO 140 is controlled by the control voltageV_(CTRL) to generate an output clock CK_(PLL) for the PLL. Furthermore,the output clock CK_(PLL) is divided by frequency divider, to providethe feedback signal CK_(DIV).

As described above, the bandwidth of the PLL 300 of FIG. 3 is associatedwith the pumping current Ip. Therefore, the PLL 300 may further includea bandwidth calibration circuit 320 capable of providing a bandwidthcontrol signal BW_CTRL to change the pumping current Ip, so as toautomatically adjust bandwidth of the PLL 300.

In some embodiments, before the feedback signal CK_(DIV) is sampled (inoperation S910), the bandwidth control signal BW_CTRL is provided tochange a slew rate of the feedback signal CK_(DIV), so as to change thepumping current Ip.

In some embodiments, the bandwidth control signal BW_CTRL is provided tochange the gain of the OTA 420 of FIGS. 5A and 5B in operation S920.When the gain of the OTA 420 is increased by the bandwidth controlsignal BW_CTRL, the current I_(OTA) is increased, and then the pumpingcurrent Ip is increased. Conversely, when the gain of the OTA 420 isdecreased by the bandwidth control signal BW_CTRL, the pumping currentIp is decreased due to the current I_(OTA) being decreased.

In some embodiments, the bandwidth control signal BW_CTRL is provided tochange the pulse width of the control signal CK_(PWM) in operation S930,so as to change the pumping current Ip.

Embodiments for track-and-hold charge pumps and PLLs for tolerating PVTvariations are provided. The track-and-hold charge pump includes atrack-and-hold circuit for sampling an input signal according to areference clock, an OTA for converting the sampled input signal into acurrent, a pulse width modulator for providing a PWM signal according tothe reference clock, and a single pumping switch. The pumping switch iscontrolled by the PWM signal to provide an output current according tothe current. It should be noted that a single pumping switch is used inthe track-and-hold charge pump, thereby avoiding charge pump noise andspurs. Furthermore, by changing the pulse width of the PWM signal, a Gmof the OTA, or a slew rate of the input signal, the current magnitude ofthe output current is changed when the slew rate is changed. In a PLL,by changing the output current of the charge pump with a bandwidthcalibration circuit, the bandwidth of the PLL is changed automatically.Therefore, if VCO noise is greater, the bandwidth calibration circuitwill provide the bandwidth control signal BW_CTRL with the higher value.Conversely, if VCO noise is lesser, the bandwidth calibration circuitwill provide the bandwidth control signal BW_CTRL with the lower value.

In some embodiments, a track-and-hold charge pump includes atrack-and-hold circuit, a transconductance amplifier, a pulse widthmodulator (PWM), and a pumping switch coupled to the transconductanceamplifier. The track-and-hold circuit samples an input signal accordingto a reference clock. The transconductance amplifier converts thesampled input signal into a current. The PWM provides a PWM signalaccording to the reference clock. The pumping switch is controlled bythe PWM signal, to provide an output current according to the current.

In some embodiments, a PLL is provided. The PLL includes avoltage-controlled oscillator (VCO), a low pass filter (LPF), afrequency divider, and a track-and-hold charge pump coupled to the LPF.The voltage-controlled oscillator provides an output clock according toa control voltage. The low pass filter filters a pumping signalcorresponding to a pumping current to provide the control voltage. Thefrequency divider divides the output clock to provide a feedback signal.The track-and-hold charge pump provides the pumping current according toa reference signal and the feedback signal. The track-and-hold chargepump includes a pumping switch coupled to the LPF, and a pulse widthmodulator (PWM). The pulse width modulator provides a PWM signal tocontrol the pumping switch according to the reference signal, so as toprovide the pumping current corresponding to the feedback signal.

In some embodiments, a PLL is provided. The PLL includes avoltage-controlled oscillator (VCO), a low pass filter (LPF), afrequency divider, a track-and-hold charge pump coupled to the LPF, anda bandwidth calibration circuit coupled to the LPF. The VCO provides anoutput clock according to a control voltage. The low pass filter filtersa pumping signal corresponding to a pumping current to provide thecontrol voltage. The frequency divider divides the output clock toprovide a feedback signal. The track-and-hold charge pump provides thepumping current via a pumping switch according to a reference signal andthe feedback signal. The bandwidth calibration circuit provides acontrol signal to the track-and-hold charge pump, so as to adjust thepumping current.

The foregoing outlines features of several embodiments so that thoseskilled in the art may better understand the aspects of the presentdisclosure. Those skilled in the art should appreciate that they mayreadily use the present disclosure as a basis for designing or modifyingother processes and structures for carrying out the same purposes and/orachieving the same advantages of the embodiments introduced herein.Those skilled in the art should also realize that such equivalentconstructions do not depart from the spirit and scope of the presentdisclosure, and that they may make various changes, substitutions, andalterations herein without departing from the spirit and scope of thepresent disclosure.

What is claimed is:
 1. A track-and-hold charge pump, comprising: atrack-and-hold circuit configured to sample an input signal according toa reference clock; a transconductance amplifier configured to convertthe sampled input signal into a current; a pulse width modulator (PWM)configured to provide a PWM signal according to the reference clock; anda pumping switch coupled to the transconductance amplifier, wherein thepumping switch is controlled by the PWM signal, to provide an outputcurrent according to the current.
 2. The track-and-hold charge pump asclaimed in claim 1, wherein the PWM modifies a pulse width of the PWMsignal according to a control signal, and current magnitude of theoutput current is changed when a pulse width of the PWM signal ischanged by the control signal.
 3. The track-and-hold charge pump asclaimed in claim 1, wherein the transconductance amplifier converts thesampled input signal into the current according to a transconductance,and current magnitude of the output current is changed when thetransconductance is changed.
 4. The track-and-hold charge pump asclaimed in claim 1, further comprising: a buffer coupled to thetrack-and-hold circuit configured to provide the input signal with aslew rate to the track-and-hold circuit, wherein current magnitude ofthe output current is changed when the slew rate is changed.
 5. Aphase-locked loop (PLL), comprising: a voltage-controlled oscillator(VCO) configured to provide an output clock according to a controlvoltage; a low pass filter (LPF) configured to filter a pumping signalcorresponding to a pumping current to provide the control voltage; afrequency divider configured to divide the output clock to provide afeedback signal; and a track-and-hold charge pump coupled to the LPFconfigured to provide the pumping current according to a referencesignal and the feedback signal; wherein the track-and-hold charge pumpcomprises: a pumping switch coupled to the LPF; and a pulse widthmodulator (PWM) configured to provide a PWM signal to control thepumping switch according to the reference signal, so as to provide thepumping current corresponding to the feedback signal.
 6. The PLL asclaimed in claim 5, wherein a bandwidth of the PLL is changed when apulse width of the PWM signal, a transconductance of thetransconductance amplifier, or a slew rate of the feedback signal ischanged.
 7. The PLL as claimed in claim 5, wherein the track-and-holdcharge pump further comprises: a track-and-hold circuit coupled to thefrequency divider configured to sample the feedback signal according tothe reference signal; and a transconductance amplifier (OTA) configuredto convert the sampled feedback signal into a current, wherein thepumping switch is coupled between the transconductance amplifier and theLPF, and the pumping switch is controlled by the PWM signal to providethe pumping current according to the current.
 8. The PLL as claimed inclaim 5, further comprising: a converter coupled to the LPF configuredto convert the pumping signal into a logic signal; and a bandwidthtracking circuit configured to provide a control signal to control thepumping signal of the PLL according to the logic signal, wherein thelogic signal indicates whether the pumping switch is turned on by thePWM signal.
 9. The PLL as claimed in claim 8, wherein the convertercomprises: a string of self-biased inverters; a capacitive elementcoupled between the LPF and an input self-biased inverter of the stringof self-biased inverters; and a string of inverters coupled between thestring of self-biased inverters and the bandwidth tracking circuit. 10.The PLL as claimed in claim 9, wherein the string of self-biasedinverters amplifies an alternating current (AC) component of the pumpingsignal to obtain an amplified signal, and the string of invertersconverts the amplified signal into the logic signal.
 11. The PLL asclaimed in claim 8, wherein the bandwidth tracking circuit comprises: aplurality of flip-flops coupled in series, wherein the logic signal isinput to a first flip-flop of the flip-flops; a plurality of firstmultipliers corresponding to the flip-flops, wherein each multipliermultiplies the logic signal by an output of the corresponding flip-flopto provide a first value; an adder configured to sum the first values toobtain a second value; an integrator configured to integrate the secondvalue; and a second multiplier configured to multiply the integratedsecond value by a weight value to provide the control signal, so as tochange a pulse width of the PWM signal, a transconductance of thetransconductance amplifier, or a slew rate of the feedback signal.
 12. Aphase-locked loop (PLL), comprising: a voltage-controlled oscillator(VCO) configured to provide an output clock according to a controlvoltage; a low pass filter (LPF) configured to filter a pumping signalcorresponding to a pumping current to provide the control voltage; afrequency divider configured to divide the output clock to provide afeedback signal; a track-and-hold charge pump coupled to the LPFconfigured to provide the pumping current via a pumping switch accordingto a reference signal and the feedback signal; and a bandwidthcalibration circuit coupled to the LPF configured to provide a controlsignal to the track-and-hold charge pump, so as to adjust the pumpingcurrent.
 13. The PLL as claimed in claim 12, wherein the bandwidthcalibration circuit comprises: a converter coupled to the LPF configuredto convert the pumping signal into a logic signal; and a bandwidthtracking circuit configured to provide the control signal to control thepumping signal according to the logic signal, wherein the logic signalindicates whether the pumping switch is turned on.
 14. The PLL asclaimed in claim 13, wherein the converter comprises: a string ofself-biased inverters; a capacitive element coupled between the LPF andan input self-biased inverter of the string of self-biased inverters;and a string of inverters coupled between the string of self-biasedinverters and the bandwidth tracking circuit.
 15. The PLL as claimed inclaim 14, wherein the string of self-biased inverters amplifies analternating current (AC) component of the pumping signal to obtain anamplified signal, and the string of inverters converts the amplifiedsignal into the logic signal.
 16. The PLL as claimed in claim 13,wherein the bandwidth tracking circuit comprises: a plurality offlip-flops coupled in series, wherein the logic signal is input to afirst flip-flop of the flip-flops; a plurality of first multiplierscorresponding to the flip-flops, wherein each multiplier multiplies thelogic signal by an output of the corresponding flip-flop to provide afirst value; an adder configured to sum the first values to obtain asecond value; an integrator configured to integrate the second value;and a second multiplier configured to multiply the integrated secondvalue by a weight value to provide the control signal.
 17. The PLL asclaimed in claim 12, wherein the track-and-hold charge pump comprises: atrack-and-hold circuit coupled to the frequency divider configured tosample the feedback signal according to the reference signal; atransconductance amplifier (OTA) configured to convert the sampledfeedback signal into a current; and a pulse width modulator (PWM)configured to provide a PWM signal to control the pumping switchaccording to the reference signal, so as to provide the pumping signalaccording to the current, wherein the pumping switch is coupled betweenthe transconductance amplifier and LPF.
 18. The PLL as claimed in claim17, wherein the PWM modifies a pulse width of the PWM signal accordingto the control signal, and magnitude of the pumping signal is changedwhen a pulse width of the PWM signal is changed by the control signal.19. The PLL as claimed in claim 17, wherein the transconductanceamplifier converts the sampled input signal into the current accordingto a transconductance, and magnitude of the pumping signal is changedwhen the transconductance is changed by the control signal.
 20. The PLLas claimed in claim 17, wherein the track-and-hold charge pump furthercomprises: a buffer coupled to the track-and-hold circuit configured toprovide the input signal with a slew rate to the track-and-hold circuit,wherein magnitude of the pumping signal is changed when the slew rate ischanged by the control signal.